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MP1583 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 1 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. the future of analog ic technology description the MP1583 is a step-down regulator with a built-in internal power mosfet. it achieves 3a of continuous output current over a wide input supply range with excellent load and line regulation. current mode operation provides fast transient response and eases loop stabilization. fault condition protection includes cycle-by-cycle current limiting and thermal shutdown. an adjustable soft-start reduces the stress on the input source at startup. in shutdown mode the regulator draws 20 a of supply current. the MP1583 requires a minimum number of external components, providing a compact solution. features ? 3a output current ? programmable soft-start ? 100m ? internal power mosfet switch ? stable with low esr output ceramic capacitors ? up to 95% efficiency ? 20 a shutdown mode ? fixed 385khz frequency ? thermal shutdown ? cycle-by-cycle over current protection ? wide 4.75v to 23v operating input range ? output adjustable from 1.22v to 21v ? under-voltage lockout applications ? distributed power systems ? battery chargers ? pre-regulator for linear regulators ?mps? and ?the future of analog ic technology? are registered trademarks of monolithic power systems, inc. typical application input 4.75v to 23v output 2.5v 3a MP1583 bs in fb sw ss gnd comp en 1 3 5 6 4 8 7 2 open = automatic startup 10nf 5.6nf 10nf 10 f ceramic 22 f ceramic 3.9k 10k 10.5k 15 h b330a MP1583_ec01 efficiency curve v in = 10v 100 90 80 70 60 50 efficiency (%) 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 load current (a) v out =5.0v v out =2.5v v out =3.3v
MP1583 ? 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 2 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. ordering information part number* package top marking free air temperature (t a ) MP1583dn soic8e MP1583dn ?40 c to +85 c MP1583dp pdip8 MP1583dp ?40 c to +85 c * for tape & reel, add suffix ?z (e.g. mp8736dl?z) for rohs compliant packaging, add suffix ?lf (e.g. mp8736dl?lf?z) package reference absolute maxi mum ratings (1) supply voltage v in .......................?0.3v to +28v switch voltage v sw ................. ?1v to v in + 0.3v bootstrap voltage v bs ....v sw ? 0.3v to v sw + 6v fb, comp and ss pins.................?0.3v to +6v continuous power dissipation (t a = +25c) (2) soic8e...................................................... 2.5w pdip8 ........................................................ 1.2w junction temperature ...............................150 c lead temperature ....................................260 c storage temperature ............. ?65 c to +150 c recommended operating conditions (3) input voltage v in ............................4.75v to 23v operating junct. temp (t j )...... -40 c to +125 c thermal resistance (4) ja jc soic8e .................................. 50 ...... 10... c/w pdip8 .................................... 104 ..... 45... c/w notes: 1) exceeding these ratings may damage the device. 2) the maximum allowable power dissipation is a function of the maximum junction temperature t j (max), the junction-to- ambient thermal resistance ja , and the ambient temperature t a . the maximum allowable continuous power dissipation at any ambient temperature is calculated by p d (max)=(t j (max)- t a )/ ja . exceeding the maximum allowable power dissipation will cause excessive die temperature, and the regulator will go into thermal shutdown. internal thermal shutdown circuitry protects the device from permanent damage. 3) the device is not guaranteed to function outside of its operating conditions. 4) measured on jesd51-7, 4-layer pcb bs in sw gnd ss en comp fb 1 2 3 4 8 7 6 5 top view soic8n/pdip8 MP1583_pd01 exposed pad (soic8n only) connect to pin 4
MP1583 ? 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 3 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. electrical characteristics v in = 12v, t a = +25 c, unless otherwise noted. parameters symbol condition min typ max units shutdown supply current v en = 0v 20 30 a supply current v en = 2.8v, v fb =1.4v 1.0 1.2 ma feedback voltage v fb 4.75v v in 23v 1.194 1.222 1.250 v error amplifier voltage gain a vea 400 v/v error amplifier transconductance g ea i comp = 10 a 500 800 1120 a/v high-side switch on-resistance r ds(on)1 0.1 ? low-side switch on-resistance r ds(on)2 10 ? high-side switch leakage current v en = 0v, v sw = 0v 0 10 a current limit 4.0 4.9 6.0 a current sense to comp transconductance g cs 3.8 a/v oscillation frequency f s 335 385 435 khz short circuit oscillation frequency v fb = 0v 25 40 55 khz maximum duty cycle d max v fb = 1.0v 90 % minimum duty cycle v fb = 1.5v 0 % en shutdown threshold voltage 0.9 1.2 1.5 v enable pull up current v en = 0v 1.1 1.8 2.5 a en uvlo threshold v en rising 2.37 2.54 2.71 v en uvlo threshold hysteresis 210 mv soft-start period c ss = 0.1f 10 ms thermal shutdown 160 c
MP1583 ? 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 4 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. typical performanc e characteristics v en 5v/div. v out 2v/div. i l 1a/div. MP1583-tpc02 soft-start c ss open, v in = 10v, v out = 3.3v, 1.5a resistive load v en 5v/div. v out 2v/div. i l 1a/div. MP1583-tpc03 v en 5v/div. v out 2v/div. i l 1a/div. 1ms/div. MP1583-tpc04 MP1583-tpc01 100 90 80 70 60 50 efficiency (%) 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 load current (a) efficiency curve v in = 7v v out =5.0v v out =2.5v v out =3.3v pin functions pin # name description 1 bs high-side gate drive bootstrap input. bs supplies the drive fo r the high-side n-channel mosfet switch. connect a 4.7nf or greater capacitor from sw to bs to power the high-side switch. 2 in power input. in supplies the power to the ic. dr ive in with a 4.75v to 23v power source. bypass in to gnd with a suitably large capacitor to eliminate noise on the input to the ic. see input capacitor 3 sw power switching output. sw is the switching node that supplies power to the output. connect the output lc filter from sw to the output load. note that a capacitor is requ ired from sw to bs to power the high-side switch. 4 gnd ground. (note: for the soic8e package, connect the exposed pad on backside to pin 4). 5 fb feedback input. fb senses the output voltage and regulates it. drive fb with a resistive voltage divider from the output voltage. the feedback threshold is 1.222v. see setting the output voltage 6 comp compensation node. comp is used to compensate the regulation control loop. connect a series rc network from comp to gnd to compensate the regulation control loop. see compensation
MP1583 ? 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 5 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. pin functions (continued) pin # name description 7 en enable/uvlo. a voltage greater than 2.71v enables operation. for complete low current shutdown the en pin voltage needs to be at less than 900mv. when the voltage on en exceeds 1.2v, the internal regulator will be enabled and the soft-start capacitor will begin to charge. the MP1583 will start switching after the en pin voltage reaches 2.71v. there is 7v zener connected between en and gnd. if en is driven by external signal, the voltage should never exceed 7v. 8 ss soft-start control input. ss cont rols the soft-start period. connect a capacitor from ss to gnd to set the soft-start period. to disable the soft-start feature, leave ss unconnected. operation the MP1583 is a current-mode step-down regulator. it regulates input voltages from 4.75v to 23v down to an output voltage as low as 1.222v, and is able to supply up to 3a of load current. the MP1583 uses current-mode control to regulate the output voltage. the output voltage is measured at fb through a resistive voltage divider and amplified through the internal error amplifier. the output current of the transconductance error amplifier is presented at comp where a rc network compensates the regulation control system. the voltage at comp is compared to the internally measured switch current to control the output voltage. the converter uses an internal n-channel mosfet switch to step-down the input voltage to the regulated output voltage. since the mosfet requires a gate voltage greater than the input voltage, a boost capacitor connected between sw and bs drives the gate. the capacitor is internally charged when sw is low. an internal 10 ? switch from sw to gnd is used to insure that sw is pulled to gnd when sw is low in order to fully charge the bs capacitor. lockout comparator error amplifier frequency foldback comparator gm = 800 a/v internal regulators 1 a 7v 1.8v slope comp clk current comparator current sense amplifier shutdown comparator ss 8 comp 6 in 2 en 7 gnd 4 oscillator 40/385khz s r q sw 3 bs 1 5v + q 1.2v + + 2.54v + 1.222v 0.7v + + fb 5 -- -- -- -- -- -- figure 1?functional block diagram
MP1583 ? 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 6 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. application information component selection setting the output voltage the output voltage is set using a resistive voltage divider from the output voltage to the fb pin. the voltage divider divides the output voltage down to the feedback voltage by the ratio: 2 1 2 r r r v v out fb + = where v fb is the feedback voltage and v out is the output voltage. thus the output voltage is: 2 2 1 22 . 1 r r r v v out + = a typical value for r2 can be as high as 100k ? , but a typical value is 10k ? . using that value, r1 is determined by: ) )( 22 . 1 ( 18 . 8 1 ? = k v v r out for example, for a 3.3v output voltage, r2 is 10k ? , and r1 is 17k ? . inductor the inductor is required to supply constant current to the output load while being driven by the switched input voltage. a larger value inductor will result in less ripple current and lower output ripple voltage. however, larger value inductors have a larger physical size, higher series resistance, and/or lower saturation current. a good rule for determining the inductance to use is to allow the inductor peak-to-peak ripple current to be approximately 30% of the maximum switch current limit. also, make sure that the peak inductor current is below the maximum switch current limit. the inductance value can be calculated by: ? ? ? ? ? ? ? ? ? = in out l s out v v 1 i f v l where v in is the input voltage, f s is the 385khz switching frequency and i l is the peak-to-peak inductor ripple current. choose an inductor that will not saturate under the maximum inductor peak current. the peak inductor current can be calculated by: ? ? ? ? ? ? ? ? ? + = in out s out load lp v v 1 l f 2 v i i where i load is the load current. table 1 lists a number of suitable inductors from various manufacturers. the choice of which inductor to use mainly depends on the price vs. size requirements and any emi requirements. table 1?inductor selection guide package dimensions (mm) vendor/ model core type core material wl h sumida cr75 open ferrite 7.0 7.8 5.5 cdh74 open ferrite 7.3 8.0 5.2 cdrh5d28 shielded ferrite 5.5 5.7 5.5 cdrh5d28 shielded ferrite 5.5 5.7 5.5 cdrh6d28 shielded ferrite 6.7 6.7 3.0 cdrh104r shielded ferrite 10.1 10.0 3.0 toko d53lc type a shielded ferrite 5.0 5.0 3.0 d75c shielded ferrite 7.6 7.6 5.1 d104c shielded ferrite 10.0 10.0 4.3 d10fl open ferrite 9.7 1.5 4.0 coilcraft do3308 open ferrite 9.4 13.0 3.0 do3316 open ferrite 9.4 13.0 5.1
MP1583 ? 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 7 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. output rectifier diode the output rectifier diode supplies the current to the inductor when the high-side switch is off. use a schottky diode to reduce losses due to the diode forward voltage and recovery times. choose a diode whose maximum reverse voltage rating is greater than the maximum input voltage, and whose current rating is greater than the maximum load current. table 2 lists example schottky diodes and manufacturers. table 2?diode selection guide diode v oltage/current rating manufacture sk33 30v, 3a diodes inc. sk34 40v, 3a diodes inc. b330 30v, 3a diodes inc. b340 40v, 3a diodes inc. mbrs330 30v, 3a on semiconductor mbrs340 40v, 3a on semiconductor input capacitor the input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the ac current to the step-down converter while maintaining the dc input voltage. use low esr capacitors for the best performance. ceramic capacitors are preferred, but tantalum or low-esr electrolytic capacitors will also suffice. since the input capacitor absorbs the input switching current it requires an adequate ripple current rating. the rms current in the input capacitor can be estimated by: ? ? ? ? ? ? ? ? ? ? ? = in out in out load c v v 1 v v i i 1 the worst-case condition occurs at v in = 2v out , where: 2 1 load c i i = for simplification, choose an input capacitor whose rms current rating is greater than half of the maximum load current. the input capacitor can be electrolytic, tantalum or ceramic. when using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor (i.e. 0.1 f) should be placed as close to the ic as possible. when using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive voltage ripple at the input. the input voltage ripple caused by capacitance can be estimated by: ? ? ? ? ? ? ? ? ? = in out in out s load in v v 1 v v c f i v 1 where c1 is the input capacitance value. output capacitor the output capacitor is required to maintain the dc output voltage. ceramic, tantalum or low esr electrolytic capacitors are recommended. low esr capacitors are preferred so as to keep the output voltage ripple low. the output voltage ripple can be estimated by: ? ? ? ? ? ? ? ? + ? ? ? ? ? ? ? ? ? = 2 8 1 1 c f r v v l f v v s esr in out s out out where l is the inductor value, c2 is the output capacitance value and r esr is the equivalent series resistance (esr) value of the output capacitor. in the case of ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance, which is the main cause for the output voltage ripple. for simplification, the output voltage ripple can be estimated by: ? ? ? ? ? ? ? ? ? = in out s out out v v 1 c l f v v 2 8 2 in the case of tantalum or electrolytic capacitors, the esr dominates the impedance at the switching frequency. for simplification, the output ripple can be approximated to: esr in out s out out r v v 1 l f v v ? ? ? ? ? ? ? =
MP1583 ? 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 8 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. the MP1583 can be optimized for a wide range of capacitance and esr values. compensation components the MP1583 employs current mode control for easy compensation and fast transient response. the system stability and transient response are controlled through the comp pin. comp is the output of the internal transconductance error amplifier. a series capacitor-resistor combination sets a pole-zero combination to control the characteristics of the control system. the dc gain of the voltage feedback loop is: out fb vea cs load vdc v v a g r a = where a vea is the error amplifier voltage gain, g cs is the current sense transconductance and r load is the load resistor value. the system has two poles of importance. one is due to the compensation capacitor (c3) and the output resistor of error amplifier while the other is due to the output capacitor and the load resistor. these poles are located at: vea ea p a c g f = 3 2 1 load p r c f = 2 2 1 2 where g ea is the error amplifier transconductance. the system has one zero of importance, due to the compensation capacitor (c3) and the compensation resistor (r3). this zero is located at: 3 3 2 1 1 r c f z = the system may have another zero of importance, if the output capacitor has a large capacitance and/or a high esr value. the zero due to the esr and capacitance of the output capacitor is located at: esr esr r c f = 2 2 1 in this case, a third pole set by the compensation capacitor (c6) and the compensation resistor (r3) is used to compensate the effect of the esr zero on the loop gain. this pole is located at: 3 6 2 1 3 r c f p = the goal of compensation design is to shape the converter transfer function to get a desired loop gain. the system crossover frequency (where the feedback loop has unity gain) is important. lower crossover frequencies result in slower line and load transient responses, while higher crossover frequencies could cause system instability. a good standard is to set the crossover frequency to approximately one-tenth of the switching frequency. the switching frequency for the MP1583 is 385khz, so the desired crossover frequency is around 38khz. table 3 lists the typical values of compensation components for some standard output voltages with various output capacitors and inductors. the values of the compensation components have been optimized for fast transient responses and good stability at given conditions. table 3?compensation values for typical output voltage/capacitor combinations (please reference fig. 3 and fig. 4) v out c2 r3 c3 c6 2.5v 22 f ceramic 3.9k ? 5.6nf none 3.3v 22 f ceramic 4.7k ? 4.7nf none 5v 22 f ceramic 7.5k ? 4.7nf none 12v 22 f ceramic 16.9k ? 1.5nf none 2.5v 560 f al. 30m ? esr 91k ? 1nf 150pf 3.3v 560 f al 30m ? esr 120k ? 1nf 120pf 5v 470 f al. 30m ? esr 100k ? 1nf 120pf 12v 220 f al. 30m ? esr 169k ? 1nf 39pf
MP1583 ? 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 9 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. to optimize the compensation components for conditions not listed in table 2, the following procedure can be used. 1. choose the compensation resistor (r3) to set the desired crossover frequency. determine r3 by the following equation: fb out cs ea c v v g g f 2 c 2 3 r = where f c is the desired crossover frequency (which typically has a value no higher than 38khz). 2. choose the compensation capacitor (c3) to achieve the desired phase margin. for applications with typical inductor values, setting the compensation zero, f z1 , below one forth of the crossover frequency provides sufficient phase margin. determine c3 by the following equation: c f 3 r 2 4 3 c > where r3 is the compensation resistor value. 3. determine if the second compensation capacitor (c6) is required. it is required if the esr zero of the output capacitor is located at less than half of the 385khz switching frequency, or if the following relationship is valid: 2 f r 2 c 2 1 s esr < if this is the case, then add the second compensation capacitor (c6) to set the pole f p3 at the location of the esr zero. determine c6 by the equation: 3 r r 2 c 6 c esr = pcb layout guide pcb layout is very important to achieve stable operation. please follow these guidelines and take figure2 and 3 for references. 1) keep the path of switching current short and minimize the loop area formed by input cap, high-side and low-side mosfets. 2) keep the connection of low-side mosfet between sw pin and input power ground as short and wide as possible. 3) ensure all feedback connections are short and direct. place the feedback resistors and compensation components as close to the chip as possible. 4) route sw away from sensitive analog areas such as fb. 5) connect in, sw, and especially gnd respectively to a large copper area to cool the chip to improve thermal performance and long-term reliability. for single layer, do not solder exposed pad of the ic c1 d1 r1 c2 r4 sgnd pgnd 5 1 2 3 4 8 7 6 fb comp en ss/ref bs in sw gnd l1 c3 c6 r2 r3 sgnd c4 c5 figure 2 D pcb layout (single layer)
MP1583 ? 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 10 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. d1 c4 r3 r2 c5 r4 l1 sgnd pgnd 1 2 3 4 8 7 6 5 fb comp en ss/ref bs in sw gnd c6 c2 c3 r1 c1 top layer bottom layer figure 3 D pcb layout (double layer) external bootstrap diode an external bootstrap diode may enhance the efficiency of the regulator, the applicable conditions of external bst diode are: z v out =5v or 3.3v; and z duty cycle is high: d= in out v v >65% in these cases, an external bst diode is recommended from the output of the voltage regulator to bst pin, as shown in fig.4 MP1583 sw bst c l bst c 5v or 3.3v out external bst diode in4148 + figure 4?add optional external bootstrap diode to enhance efficiency the recommended external bst diode is in4148, and the bst cap is 0.1~1f.
MP1583 ? 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 11 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. typical application circuits input 4.75v to 23v output 3.3v 3a c1 10 f/25v ceramic c2 22 f/10v murata c3 4.7nf c4 10nf c6 ns d1 c5 10nf l1 15 h r3 4.7k r2 10k r1 16.9k MP1583 bs in fb sw ss gnd comp en 1 3 5 6 4 8 7 2 open = automatic startup figure 5?3.3v output 3a solution with murata 22f, 10v ceramic output capacitor
MP1583 ? 3a, 23v, 385khz step-down converter MP1583 rev. 3.1 www.monolithicpower.com 12 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. package information soic8e (exposed pad) see detail "a" 0.0075(0.19) 0.0098(0.25) 0.050(1.27) bsc 0.013(0.33) 0.020(0.51) seating plane 0.000(0.00) 0.006(0.15) 0.051(1.30) 0.067(1.70) top view front view side view bottom view note: 1) control dimension is in inches. dimension in bracket is in millimeters. 2) package length does not include mold flash, protrusions or gate burrs. 3) package width does not include interlead flash or protrusions. 4) lead coplanarity (bottom of leads after forming) shall be 0.004" inches max. 5) drawing conforms to jedec ms-012, variation ba. 6) drawing is not to scale. 0.089(2.26) 0.101(2.56) 0.124(3.15) 0.136(3.45) recommended land pattern 0.213(5.40) 0.063(1.60) 0.050(1.27) 0.024(0.61) 0.103(2.62) 0.138(3.51) 0.150(3.80) 0.157(4.00) pin 1 id 0.189(4.80) 0.197(5.00) 0.228(5.80) 0.244(6.20) 14 85 0.016(0.41) 0.050(1.27) 0 o -8 o detail "a" 0.010(0.25) 0.020(0.50) x 45 o 0.010(0.25) bsc gauge plane
MP1583 ? 3a, 23v, 385khz step-down converter notice: the information in this document is subject to change wi thout notice. please contact m ps for current specifications. users should warrant and guarantee that third party intellectual property rights ar e not infringed upon when integrating mps products into any application. mps will not assume any legal responsibility for any said applications. MP1583 rev. 3.1 www.monolithicpower.com 13 6/20/2011 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2011 mps. all rights reserved. pdip8 note: 1) control dimension is in inches . dimension in bracket is millimeters . 0.021(0.533) 0.015(0.381) 0.100 bsc(2.540) 0.145(3.683) 0.134(3.404) 0.140(3.556) 0.120(3.048) 0.035 (0.889) 0.015 (0.381) 0.260 (6.604) 0.240 (6.096) 0.387 (9.830) 0.367 (9.322) pin 1 ident. 0.040 (1.016) 0.020 (0.508) 0.065 (1.650) 0.050 (1.270) 0.014 (0.356) 0.008 (0.200) 0.325(8.255) 0.300(7.620) 0.392(9.957) 0.332(8.433) 3 ~ 11 lead bend

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